Electronic Ballast Having A Flyback Cat-Ear Power Supply

ABSTRACT

An electronic ballast for driving a gas discharge lamp includes a rectifier to convert an AC mains input voltage to a rectified voltage, a valley-fill circuit for producing a DC bus voltage, an inverter for converting the DC bus voltage to a high-frequency AC voltage for driving the lamp, a control circuit for controlling the inverter, and a flyback cat-ear power supply for supplying current to the inverter when the rectified voltage is less than a predetermined level. The flyback cat-ear power supply also provides power to the control circuit. Preferably, the flyback cat-ear power supply draws current only when the inverter is not drawing current directly from the AC mains, so as to make the input current to the ballast substantially sinusoidal. The result is a ballast having substantially improved power factor and THD. Also, the ballast operates more efficiently because the flyback cat-ear ear power supply supplies excess energy not needed by the ballast control circuitry to the inverter to be used to drive the lamp.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a continuation of co-pending, commonly-assigned U.S.patent application Ser. No. 11/483,374, filed Jul. 7, 2006, entitledELECTRONIC BALLAST HAVING A FLYBACK CAT-EAR POWER SUPPLY, the entiredisclosure of which is hereby incorporated by reference.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to electronic ballasts and, moreparticularly, to electronic dimming ballasts for gas discharge lamps,such as fluorescent lamps.

2. Description of the Related Art

Electronic ballasts for fluorescent lamps typically include a “frontend” and a “back end”. The front end typically includes a rectifier forchanging alternating-current (AC) mains line voltage to a direct-current(DC) bus voltage and a filter circuit for filtering the DC bus voltage.The ballast back end typically includes a switching inverter forconverting the DC bus voltage to a high-frequency AC voltage, and aresonant tank circuit having a relatively high output impedance forcoupling the high-frequency AC voltage to the lamp electrodes.

The front end of electronic ballasts also often include a boostconverter, which is an active circuit for boosting the magnitude of theDC bus voltage above peak of line voltage, and for improving the totalharmonic distortion (THD) and power factor of the input current to theballast. However, boost converters typically include integrated circuits(IC) and semiconductor switches, such as field effect transistors(FETs). In order to handle the amount of current required to drive thelamp at high end (i.e. at or near 100% light intensity), the componentsof such a boost converter are typically large and costly.

A prior art ballast 100 will be described with reference to the blockdiagram shown in FIG. 1 and the voltage and current waveforms shown inFIGS. 2 a-2 d and is explained in greater detail in U.S. Pat. No.6,674,248, issued on Jan. 6, 2004, entitled “Electronic Ballast”, whichis herein incorporated by reference in its entirety.

The ballast 100 includes an electromagnetic interference (EMI) filter115 and a rectifier 120 both capable of being connected to an AC powersupply such as a typical 120V, 60 Hz AC main. The EMI filter 115isolates high-frequency noise generated by the ballast circuitry fromthe AC power supply. The rectifier 120 converts the AC input voltage toa rectified pulsating DC voltage 210, which has a maximum value ofV_(PEAK) (shown as 230 in FIG. 2 a). For example, if the AC inputvoltage has an RMS (root mean square) value of 277V, the value ofV_(PEAK) will be approximately 392V. The rectifier 120 is connected to avalley-fill circuit 130 through a diode 140. A high-frequency filtercapacitor 150 is connected across the inputs to the valley-fill circuit130. The valley-fill circuit 130 selectively charges and discharges anenergy-storage device, such as one or more capacitors, so as to fill the“valleys” between successive rectified voltage peaks to produce asubstantially DC bus voltage 220. The DC bus voltage is the greater ofeither the rectified voltage, or the voltage across the energy storagedevice in the valley-fill circuit 130.

The outputs of the valley-fill circuit 130 are in turn connected to theinputs to an inverter 160. The inverter 160 converts the rectified DCvoltage to a high-frequency AC voltage. The outputs of the inverter 160are connected to an output circuit 170, which typically includes aresonant tank, and may also include a coupling transformer. The outputcircuit filters the inverter 160 output to supply essentially sinusoidalvoltage, as well as provide voltage gain and increased output impedance.The output circuit 170 is capable of being connected to drive a load 180such as a gas discharge lamp; for example, a fluorescent lamp.

An output current sense circuit 185 coupled to the load 180 providesload current feedback to a control circuit 190. The control circuit 190generates control signals to control the operation of the valley-fillcircuit 130 and the inverter 160 so as to provide a desired load currentto the load 180. A power supply 110 is connected across the outputs ofthe rectifier 120 to provide the necessary power for proper operation ofthe control circuit 190.

A schematic representation of a prior art valley-fill circuit 330 thatmay be used with ballast 100 is shown in FIG. 3 a. The rectifiedpulsating DC voltage 210 (in FIG. 2 a) is provided to the valley-fillcircuit 330 through diode 140. Two energy-storage capacitors 280, 282are provided in the valley-fill circuit 330. These energy-storagecapacitors 280, 282 charge in series with a charging current flowingthrough capacitor 280, diode 284, capacitor 282, and a resistor 286,which limits the magnitude of the charging current. The energy-storagecapacitors 280, 282 are sized such that the same voltage, thevalley-fill voltage V_(VF) (shown as 235 in FIG. 2 a), is producedacross each capacitor. The magnitude of the valley-fill voltage V_(VF)is approximately one-half of the peak, V_(PEAK), of the rectifiedpulsating DC voltage 210, which is about 200V when V_(PEAK) is 392V.However, the energy-storage capacitors 280, 282 discharge in parallel,with current flowing through diode 288 to allow capacitor 280 todischarge, and through diodes 290 and 292 to allow capacitor 282 todischarge. Thus, a DC bus voltage 220 is formed across the valley-fillcircuit 330 as shown in FIG. 2 b.

When the rectified voltage 210 is greater than the valley-fill voltageV_(VF), i.e. one-half of the peak of the AC mains line voltage, theinverter 160 draws current directly from the AC power supply, throughthe EMI filter 115 and the rectifier 120, to drive the lamp. When therectified voltage 210 is less than the valley-fill voltage V_(VF), thenthe inverter 160 draws current from the energy-storage capacitors inparallel. This results in the ballast drawing an input current 240 fromthe AC mains only during a relatively large duration of each linehalf-cycle centered about the peak of the line voltage, which allows forunwanted harmonics and undesirable total harmonic distortion (THD).

In order to lower the THD, the input current of the ballast should be assinusoidal as possible (as shown by 250 in FIG. 2 c). One approach tomaking the input current more sinusoidal is to implement power supply110 as a cat-ear power supply, which ideally draws an input current 260(shown in FIG. 2 d) near the zero crossing of the AC mains input voltagewaveform at either the leading edge of each half-cycle, or the trailingedge of each half-cycle, or both. When the current drawn by the cat-earpower supply is added to the inverter current 240, the input currentwaveform is shaped to be more nearly sinusoidal, such that the inputcurrent THD is substantially reduced, and the power factor of theballast is increased. The cat-ear power supply derives its name from theshape of its input current waveform that “fills in” the current waveformdrawn by the ballast from the AC mains around the zero crossings (theshape resembling the ears of a cat). That is, the input current waveformtypically rises from zero sinusoidally to a value substantially belowpeak, then falls sharply to zero, or rises from zero sharply to a valuesubstantially below peak, then falls sinusoidally to zero. The cat-earpower supply typically “steals” power from the line when the back end isnot drawing current directly from the line. The cat-ear power supply maybe provided with circuitry that “cuts in” and “cuts out” the powersupply in response to fixed input voltage levels. Along with helping toreduce THD and improve power factor, the cat-ear power supply alsosupplies the power necessary to operate the control circuit 190.

A prior art cat-ear power supply 310 is shown in FIG. 3 b. The cat-earpower supply 310 is designed with fixed voltage cut-in and cut-outpoints and will only draw current from the AC mains when the rectifiedvoltage 210 is below a predetermined value. This condition will occurfrom a predetermined time before a line voltage zero crossing to apredetermined time after the line voltage zero crossing. The cut-out andcut-in voltage points can be adjusted so that the cat-ear power supply310 draws current during a first interval from a time just after theline voltage zero crossing to a time when the energy storage capacitorin the valley-fill circuit 130 begins drawing charging current from theline, and during a second interval from a time when the valley-fillenergy storage capacitor stops drawing charging current from the lineuntil the next line voltage zero crossing.

When the rectified voltage 210 is lower than a predetermined voltage, acharging field effect transistor (FET) 312 conducts to allow charging ofenergy-storage capacitor 314, which charges toward a voltage V_(CC).Alternatively, when the rectified line voltage is equal to or greaterthan the predetermined voltage, then cut-out transistor 318 beginsconducting. The collector of the cut-out transistor 318 pulls thecathode of a Zener diode 320 toward V_(CC), which effectively turns offthe charging FET 312. The predetermined cut-in and cut-out voltages aredetermined by the resistive voltage divider network including resistors322 and 324, to which the base of the cut-out transistor 318 isconnected.

The rate of charge of the capacitor 314 is determined by a resistor 316in series with the drain of the MOSFET transistor 312. To allow for asubstantially piece-wise continuous ballast input current, the value ofthe current drawn by cat-ear power supply 310 should be substantiallythe same as the current that will be drawn by the back end of theballast 100 at the predetermined cut-out and cut-in times. Inconjunction with the value of the capacitor 314, resistor 316 can bechosen so that the current drawn will have a desired maximum currentthat is substantially the same as the current that will be drawn by theback end at the predetermined cut-out and cut-in times and such that thecurrent drawn will substantially match the shape of the AC mainsvoltage.

However, the current drawn from V_(CC) by the control circuit 190 ofballast 100 is not constant throughout the operation of the ballast.Consequently, the current required to charge capacitor 314 is sometimessmaller, thus the time required to charge capacitor 314 is shorter.Therefore, the current drawn by cat-ear supply 310 sometimes does notreach the desired maximum current at the predetermined cut-out andcut-in times as shown by 360 in FIG. 3 c. When the cat-ear supply inputcurrent 360 is added to the current 240 drawn by the back end, theresulting ballast input current 370 (shown in FIG. 3 d) is notcompletely sinusoidal, thus contributing to the THD of the ballast.

Additionally, in order to obtain the appropriate shape of the inputcurrent waveform, the power dissipated by the resistor may be verylarge. For example, the power into the cat-ear power supply with theinput current 260 (in FIG. 2 d) may be approximately four watts eachhalf-cycle. If the maximum power consumption of the control circuit 190is approximately 0.5 watts, then 3.5 watts must be dissipated in theresistor 316 during each half-cycle. This means that the resistor 316must be physically large in order to handle the required powerdissipation.

Thus, there exists a need for a cat-ear power supply for an electronicballast that is more efficient and draws the appropriate amount ofcurrent when the back end is not drawing current directly from the linein order to reduce the THD of the ballast. Further, there exists a needfor an electronic dimming ballast that has the reduced THD of a ballasthaving an active boost converter, but does not require the large,expensive components of such boost converters.

SUMMARY OF THE INVENTION

According to an embodiment of the present invention, an electronicballast, which draws an input current from an AC power supply and drivesa gas discharge lamp, comprises: (1) a rectifier for rectifying an ACinput voltage from said AC power supply to produce a rectified voltage;(2) a filter circuit for converting said rectified voltage to a filteredbus voltage; (3) an inverter for converting said bus voltage to ahigh-frequency AC drive voltage to drive said lamp; (4) a controlcircuit coupled to the inverter for controlling the operation of saidinverter; and (5) a ballast power supply that receives said rectifiedvoltage and generates a substantially DC voltage for powering saidcontrol circuit. The ballast power supply selectively draws current fromsaid AC power supply when said rectified voltage is lower than apredetermined value such that said input current to said ballast isessentially sinusoidal. The ballast power supply is coupled to saidinverter and is operable to provide current to said inverter when themagnitude of said rectified voltage is less than said predeterminedlevel.

According to another embodiment of the present invention, an electronicballast for driving a gas discharge lamp comprises a rectifier, aninverter, a first circuit coupled from the rectifier to the inverter,and a second coupled from the rectifier to the inverter in parallelelectrical connection with the first circuit. The rectifier rectifiesthe AC input voltage from said AC power supply to produce a rectifiedvoltage, while the inverter generates a high-frequency AC drive voltageto drive said lamp. The first circuit supplies current from said ACpower supply to said inverter and provides said rectified voltage tosaid inverter when the magnitude of said rectified voltage is greaterthan a predetermined value. The second circuit supplies current to saidinverter and provides a boosted voltage to said inverter when themagnitude of said rectified voltage is less than said predeterminedvalue. The magnitude of said boosted voltage is greater than themagnitude of said rectified voltage when the magnitude of said rectifiedvoltage is less than said predetermined value.

According to another aspect of the present invention, an electronicballast for driving a gas discharge lamp comprises a rectifier forrectifying an AC line voltage to produce a rectified voltage, and aboost converter for receiving said rectified voltage and producing asubstantially DC output voltage having an average magnitude less than apeak value of said rectified voltage.

A cat-ear circuit for an electronic ballast having a front end forreceiving an AC input voltage and a back end for driving a gas dischargelamp is also described herein. The cat-ear circuit comprises an inputfor receipt of a rectified voltage, a semiconductor switch, atransformer, a control circuit, and first and second outputs. Thesemiconductor switch is coupled in series electrical connection betweensaid input and a circuit common and has a conductive state and anon-conductive state. The transformer has a primary winding and asecondary winding, where said primary winding coupled in serieselectrical connection with said semiconductor switch. The controlcircuit is operable to receive said rectified voltage and to repeatedlyswitch said semiconductor switch at a high frequency between saidconductive state and said non-conductive state only when said rectifiedvoltage is below a predetermined level, such that a boosted voltage isproduced across said secondary winding of said transformer. The firstoutput for provides said boosted voltage to said ballast back end onlywhen said rectified voltage is below said predetermined level, and thesecond output provides a substantially low-magnitude DC voltage.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a simplified block diagram of a prior art electronic ballast;

FIG. 2 a is a simplified waveform diagram illustrating the rectifiedvoltage of the ballast of FIG. 1;

FIG. 2 b is a simplified waveform diagram illustrating the DC busvoltage of the ballast of FIG. 1;

FIG. 2 c is a simplified waveform diagram illustrating the input currentof the ballast of FIG. 1;

FIG. 2 d is a simplified waveform diagram illustrating the ideal inputcurrent of a cat-ear power supply of the ballast of FIG. 1;

FIG. 3 a is a simplified schematic of a prior art valley-fill circuitthat may be used with the ballast of FIG. 1;

FIG. 3 b is a simplified schematic of a prior art cat-ear power supplythat may be used with the ballast of FIG. 1;

FIG. 3 c is a simplified waveform diagram illustrating the input currentof the prior art cat-ear power supply of FIG. 3 b;

FIG. 3 d is a simplified waveform diagram illustrating the input currentof the ballast of FIG. 1 including the cat-ear power supply of FIG. 3 b;

FIG. 4 is a simplified block diagram of the electronic ballast of thepresent invention; and

FIG. 5 is a simplified schematic of the flyback cat-ear power supply ofthe present invention.

DETAILED DESCRIPTION OF THE INVENTION

The foregoing summary, as well as the following detailed description ofthe preferred embodiments, is better understood when read in conjunctionwith the appended drawings. For the purposes of illustrating theinvention, there is shown in the drawings an embodiment that ispresently preferred, in which like numerals represent similar partsthroughout the several views of the drawings, it being understood,however, that the invention is not limited to the specific methods andinstrumentalities disclosed.

Referring to FIG. 4, there is shown a simplified schematic diagram of anelectronic ballast 400 constructed in accordance with the invention. Aflyback cat-ear power supply 410 is coupled to the output of therectifier 120. A flyback converter can be defined as a buck-boostswitch-mode power supply topology in which, during the first period of aswitching cycle, the energy is stored in an inductance, and during thesecond period, this energy is transferred to a different winding of thesame inductor and into the load. Flyback converters are well known inthe art and are defined further in “Principles of Power Electronics” byJohn G. Kassakian et al., Addison-Wesley Publishing Company, 1991,chapter 7, pp. 139-165, which is herein incorporated by reference in itsentirety. The flyback cat-ear power supply 410 includes a first output412 coupled to the input of the valley-fill circuit 130, a second output414 providing a 15 VDC supply voltage for powering a control circuit490, and a third output 416 providing an isolated 15 V_(DC) supplyvoltage. Ballast 400 further comprises a sensor interface circuit 492that receives the isolated 15 V_(DC) supply from the flyback cat-earpower supply 410 and provides the supply to a device external to theballast (not shown), such as an occupancy sensor or a photosensor. Thesensor interface circuit 492 also receives control signals from theexternal devices and relays these control signals to the control circuit490.

The flyback cat-ear power supply 410 of the current invention is shownin greater detail in FIG. 5. The rectified voltage at the output of therectifier 120 is provided to one side of the primary winding 512 of aflyback transformer 510. A FET 520 is provided in series with theprimary winding 512 of the flyback transformer 510 and a current senseresistor 530. The transformer 510 also includes a secondary winding 514that is coupled to two diodes 522, 524. Note that current does not flowsimultaneously in the primary and secondary windings of a flybacktransformer.

A flyback control circuit 540, comprising a timing circuit 542, anoscillator 544, and a peak current limit circuit 546, controls theconduction state of the FET 520. Oscillator 544 produces a square wavehaving a constant frequency and a constant duty cycle for driving theFET 520. Preferably, the frequency and duty cycle of the square waveproduced by the oscillator 544 are 140 kHz and 50%, respectively. Theduty cycle is selected to provide the minimal THD for the ballast 400.The square wave is provided to a control input of FET 520.

The timing circuit 542 determines when the flyback cat-ear power supply410 should be drawing current from the AC mains and controls theoscillator 544 accordingly. Since the flyback cat-ear power supply 410should draw current when the output of the rectifier 120 is below the DCbus voltage, the timing circuit 542 detects when the voltage at theoutput of the rectifier 120 is below the valley-fill voltage V_(VF)(i.e. approximately 200V) and drives the oscillator 544 to beginoscillating. When the output of the rectifier 120 is above thevalley-fill voltage, the timing circuit 542 causes the oscillator 544 tostop oscillating.

Peak current limit circuit 546 monitors the voltage across current senseresistor 530 and thus the current through FET 520. If peak current limitcircuit 546 detects an over-current condition in FET 520, i.e. when thecurrent exceeds a limit that ensures normal operation of the FET, thepeak current limit circuit causes oscillator 544 to interrupt thepresent oscillation cycle, thus causing the FET to stop conducting.

As oscillator 544 drives the FET 520 with the square wave, the FETswitches between conductive and non-conductive states. When the FET 520is conducting, current flows through the magnetizing inductance of theprimary side 512 of transformer 510. At this time, current does not flowin the secondary winding 516 because of the orientation of diodes 522,524. When the FET 520 is non-conducting, the energy that is stored inthe magnetizing inductance is transferred to the secondary winding 516and a voltage is produced across the secondary winding. The flybackcat-ear power supply 410 operates in a discontinuous mode, which meansthat all energy that is stored in the primary winding 512 is transferredto the secondary winding 514 and there is a time that the currentsthrough the transformer reach a value of zero each cycle. The voltageproduced on the secondary winding 514 is dependent on the turns ratio oftransformer 510, the frequency of the current through the FET 520, andthe duty cycle of the current through FET 520. Because the frequency andduty cycle of the square wave are fixed, no feedback from the secondaryside 514 of transformer 510 back to flyback control circuit 540 isneeded.

When the voltage at the output of the rectifier 120 is below the DC busvoltage, the oscillator 544 is actively switching the FET 520 and avoltage having a magnitude approximately equal to the valley-fillvoltage V_(VF) is produced across the secondary winding 514 oftransformer 510. This voltage is provided through diode 522 to the firstoutput 412, which is coupled to the input of the valley-fill circuit130. In this way, when the voltage at the output of the rectifier 120 isnot great enough to supply current to the inverter 170, the flybackcat-ear power supply is capable of supplying current to the inverterthrough the first output 412. Since the first output 412 is coupled tothe valley-fill circuit 130, the voltage at first output 412 is limitedto the DC bus voltage 220, which has an average magnitude less than apeak value of the rectified voltage, e.g., approximately one-half of thepeak of the rectified voltage, when the voltage at the output of therectifier 120 is below the DC bus voltage.

The secondary winding 514 of the transformer 510 includes a tap that isprovided to the anode of the diode 524. When the FET 520 is switching, avoltage of approximately 20V is produced from the tap to circuit common.This voltage is provided to a first 15V regulated linear power supply550, having an input energy storage capacitor 552 and an output energystorage capacitor 554. The linear power supply 550 provides a regulatedDC output of 15 volts to second output 414 of the flyback cat-ear powersupply 410 for powering the control circuit 490 of the ballast 400. The15V linear power supply 550 tightly controls the regulated DC outputvoltage to remain within specified limits despite variations in theinput voltage or the load current.

Additionally, the transformer 510 includes an auxiliary winding 516 thatis provided to a second 15V regulated linear power supply 560 through adiode 566. The 15V linear power supply 560 has an input energy storagecapacitor 562 and an output energy storage capacitor 564. The linearpower supply 560 provides an isolated DC output of 15 volts at thirdoutput points 416A and 416B. The auxiliary winding 516 is notelectrically connected to the rest of the ballast circuit and thus theisolated DC output of the 15V regulated linear power supply 560 iselectrically isolated from any high voltage points in the rest of theballast circuitry. This is desirable for safety concerns when poweringexternal low-voltage devices, such as occupancy sensors andphotosensors, from the ballast.

To minimize the THD of the ballast, the input current of the ballastshould be as sinusoidal and continuous as possible. The input current ofthe ballast is the combination of the current drawn directly from the ACline by the inverter, and the input current drawn from the AC line bythe power supply. The current drawn from the AC line by the inverter 160is determinable (shown as 240 in FIG. 2C). The desired input current 260for the flyback cat-ear power supply is one that will cause the totalballast input current 250 to be as sinusoidal as possible. The desiredpeak value 262 of the flyback cat-ear power supply input current 260 cantherefore be determined from the ballast input current 240 due to theinverter with the ballast at high-end. Since the AC input voltage,v_(AC)(t), and the shape and peak value of the desired current draw,i_(PS)(t), of the flyback cat-ear power supply are known, a desiredaverage power for the flyback cat-ear power supply, P_(DESIRED), can becalculated using the equation

P _(DESIRED) =∫v _(AC)(t)*i _(PS)(t)dt.  (Equation 1)

For example, for a ballast with an AC input voltage of 277 V_(RMS),driving three T8 lamps (32 watts each), and a ballast factor of 0.85,the desired average power consumption of the power supply is 4 W inorder to obtain the optimal THD of the ballast at high-end.

The flyback cat-ear power supply 410 provides outputs to the input ofthe inverter 160 (through the first output 412), the ballast controlcircuit 490 (through the second output 414), and, optionally, externalsensors (through the third output 416). The average power consumption ofeach of the outputs of the flyback cat-ear power supply 410, plus anypower that is dissipated in the power supply during the conversionprocess, must total up to the desired average power consumption,P_(DESIRED). Since the ballast control circuit 490, and any externalsensors, will not typically require enough power to total up toP_(DESIRED), the power dissipated in the power supply and the powersupplied to the inverter 160 must account for the rest of the desiredpower consumption.

Because the flyback cat-ear power supply 410 has a path through thefirst output 412 to supply power to the inverter 160, the excess of thedesired average power consumption, P_(DESIRED), does not need to bewastefully dissipated in the power supply. For example, consider thefollowing power requirements of the ballast 400:

-   -   Power into the flyback cat-ear power supply 410 is 4 watts.    -   Power consumption of the ballast control circuit 490 is 0.5        watts.    -   Power consumption of an external occupancy sensor is 0.5 watts.    -   Power unavoidably lost during the conversion process is 0.5        watts.        The difference between the power into the power supply and the        total power consumed (i.e., the excess power) is 2.5 watts,        which is provided through the first output 412 to the inverter        160. Prior art cat-ear power supplies, such as power supply 310        shown in FIG. 3 b, did not provide a path to supply power to the        inverter 160, so the excess power was dissipated in the large        resistor 316. Considering the example from above, the resistor        would be required to dissipate 2.5 watts.

The power that is consumed by the ballast control circuit 490, and anyexternal sensors, is not constant. Even though the average powerconsumption of these components may be determinable, the instantaneouspower may vary greatly, which can also produce variations in the inputcurrent of the flyback cat-ear power supply 410. However, the flybackcat-ear power supply of the present invention is capable of supplying tothe inverter 160 any excess power that is not consumed by the ballastcontrol circuit 490 and any external sensors. Considering the examplefrom the previous paragraph, if the power consumption of the ballastcontrol circuit 490 drops to zero, then three watts of excess power willbe supplied to the inverter 160. Note that when driving a lamp at anyintensity, the back end of the ballast will always consume at least theexcess amount of power that is drawn by the flyback cat-ear power supply410.

Thus, no excess power is lost in the flyback cat-ear power supply 410 ofthe present invention, but instead the excess power is provided to theinverter 160 to drive the lamp. Thus, the flyback cat-ear power supply410 is more efficient, and is operable to draw current until the momentthat the inverter 160 begins drawing current from the AC power supply,independent of the power consumption of the ballast control circuit 490or any external sensors. The result is an input current to the ballastthat is more continuous, resulting in a lower THD.

As mentioned above, to minimize the THD of the ballast, the inputcurrent must be as sinusoidal as possible (i.e. ideally, the shape ofthe input current follows the shape of the AC mains line voltage).Therefore, the ballast should ideally appear to the AC power supply as aresistive load having a constant resistance. Certain parameters of theflyback cat-ear power supply 410 can be set such that the ballastappears as a substantially resistive load to the AC power supply whenthe cat-ear power supply is drawing current. The value of the inductanceof the primary side 412 of transformer 410 and the values of thefrequency and the duty cycle of the square wave driving FET 520,determine the shape and peak value of the current drawn by the flybackcat-ear power supply 410.

The impedance, R_(IN), looking into the ballast when the flyback cat-earpower supply 410 is drawing current is essentially the value of the ACmains line voltage divided by the input current of the ballast or:

R _(IN) =v _(AC) /i _(IN).  (Equation 2)

Since the period of the switching of the FET 520 is very small incomparison to the period of the line cycle, the AC mains line voltagev_(AC) is substantially constant throughout the period of the switchingcycle of the FET. When the FET 520 is conducting, the voltage v_(L)across the inductance L of the primary winding 412 is essentially equalto the AC mains line voltage, i.e., v_(L)=v_(AC). The voltage v_(L) isequal to the inductance L multiplied by di_(L)/dt, i.e., the change inthe current through the primary winding as a function of time, as shownby:

v _(L) =L*(di _(L) /dt).  (Equation 3)

Since the flyback cat-ear power supply is operating in discontinuousmode, the change in current, di_(L), each period is from zero to a peakvalue, I_(L-PK), resulting in di_(L)=I_(L-PK). The change in time, dt,is the duty cycle D of the switching of FET 520 times the period, i.e.,dt=D*T. The period T is the inverse of the frequency f, i.e., T=1/f.Thus, equation 3 simplifies to:

v _(AC) =L*(f*I _(L-PK) /D).  (Equation 4)

Since the EMI filter 115 isolates high-frequency signals from the ACpower supply, the input current to the ballast, i_(IN), is equal to theaverage value of the inductor current, as shown by:

i _(IN) =i _(L-AV)=(1/T)∫i _(L)(t)dt.  (Equation 5)

The integral of the current through the primary winding can be easilysolved for by noting that the area under the curve of a triangle issimply one half of the base times the height, and thus:

i _(N)=(1/T)*(½)*(D*T)*I _(L-PK)=(½)*D*I _(L-PK).  (Equation 6)

Therefore, substituting v_(AC) from equation 4 and i_(IN) equation 6into equation 2, the impedance R_(IN) of the ballast can be calculatedas:

R _(IN) =v _(AC) /i _(IN)=2*L*f/D ².  (Equation 7)

Since the inductance of the primary winding, the frequency and the dutycycle of the switching of FET 520 are constant, the impedance R_(IN) isalso constant. Thus, the flyback cat-ear power supply draws a currentthat is proportional to the AC mains voltage, and hence follows theshape of the AC mains voltage. The inductance of the primary winding,the frequency and the duty cycle of the switching of FET 520 can bedetermined such that the input current to the flyback cat-ear powersupply is the same value as the input current that the inverter willdraw at the moment that the flyback cat-ear power supply stops drawingcurrent and the inverter begins drawing current. Thus, the current drawnfrom the AC mains can be made more nearly continuous.

Since the flyback cat-ear power supply 410 provides power to theinverter 160 during the time period when the valley-fill capacitors 280,282 provide power to the inverter, the ballast of the present inventionhas further advantages over the ballasts of the prior art. First,because less current is drawn from the valley-fill capacitors 280, 282to drive the inverter 160, the DC bus voltage 220 drops less during thevalleys between successive rectified voltage peaks. The valley-fillcapacitors 280, 282 can thus have a smaller capacitance, which meansthat the physical size of the capacitors will also be smaller. Finally,since less energy is needed to recharge the valley-fill capacitors 280,282, the charging currents of the capacitors when the inverter 160 stopsdrawing current from the flyback cat-ear power supply 410 and beginsdrawing current directly from the AC line will be of smaller magnitude.This results in improved ballast input current wave shape during thetime when the inverter 160 is drawing current directly from the ACmains.

Although the present invention has been described in relation toparticular embodiments thereof, many other variations and modificationsand other uses will become apparent to those skilled in the art. It ispreferred, therefore, that the present invention be limited not by thespecific disclosure herein, but only by the appended claims.

1. An electronic ballast for driving a gas discharge lamp, said ballastdrawing an input current from an AC power supply, said ballastcomprising: a rectifier for rectifying an AC input voltage from said ACpower supply to produce a rectified voltage; a filter circuit forconverting said rectified voltage to a filtered bus voltage; an inverterfor converting said bus voltage to a high-frequency AC drive voltage todrive said lamp; a control circuit coupled to the inverter forcontrolling the operation of said inverter; and a ballast power supplycoupled to receive said rectified voltage for selectively drawingcurrent from said AC power supply when said rectified voltage is lowerthan a predetermined value such that said input current to said ballastis essentially sinusoidal, said ballast power supply operable togenerate a substantially DC voltage for powering said control circuit;wherein said ballast power supply is coupled to said inverter and isoperable to provide current to said inverter when the magnitude of saidrectified voltage is less than said predetermined level.
 2. Theelectronic ballast according to claim 1, wherein said ballast powersupply includes a cat-ear power supply.
 3. The electronic ballastaccording to claim 1, wherein said ballast power supply includes aflyback cat-ear power supply.
 4. The electronic ballast according toclaim 3, wherein said cat-ear power supply includes a flyback controlcircuit operable to cause said cat-ear power supply to draw current fromsaid AC power supply when said rectified voltage is lower than saidpredetermined level.
 5. The electronic ballast according to claim 3,wherein said cat-ear power supply includes a flyback control circuitoperable to cause said cat-ear power supply to draw current from said ACpower supply when said current drawn by said inverter from said AC powersupply is substantially zero amps.
 6. The electronic ballast accordingto claim 2, wherein said cat-ear power supply includes a first outputfor supplying current to said inverter and a second output for supplyingpower to said control circuit.
 7. An electronic ballast for driving agas discharge lamp, said ballast drawing an input current from an ACpower supply, said ballast comprising: a rectifier for rectifying saidAC input voltage from said AC power supply to produce a rectifiedvoltage; an inverter for generating a high-frequency AC drive voltage todrive said lamp; a first circuit coupled from said rectifier to saidinverter for supplying current to said inverter, said first circuitoperable to provide current from said AC power supply to said inverterand to provide said rectified voltage to said inverter when themagnitude of said rectified voltage is greater than a predeterminedvalue; and a second circuit coupled from said rectifier said inverter inparallel electrical connection with said first circuit for supplyingcurrent to said inverter, said second circuit operable to providecurrent to said inverter and to provide a boosted voltage to saidinverter when the magnitude of said rectified voltage is less than saidpredetermined value; wherein the magnitude of said boosted voltage isgreater than the magnitude of said rectified voltage when the magnitudeof said rectified voltage is less than said predetermined value. 8-14.(canceled)
 15. An electronic ballast for driving a gas discharge lampcomprising: a rectifier for rectifying an AC line voltage to produce arectified voltage; and a boost converter for receiving said rectifiedvoltage and producing a substantially DC output voltage having anaverage magnitude less than a peak value of said rectified voltage. 16.The electronic ballast according to claim 15, wherein said boostconverter produces said output voltage for only a portion of a halfcycle of said AC line voltage.
 17. The electronic ballast according toclaim 15, wherein said boost converter produces said output voltage whensaid rectified voltage is less than a predetermined level.
 18. Theelectronic ballast according to claim 17, further comprising: aninverter for receiving said DC output voltage and for producing ahigh-frequency AC drive voltage to be supplied to said lamp.
 19. Theelectronic ballast according to claim 18, wherein said inverter isoperable to convert said output voltage of said boost converter to saidhigh-frequency AC drive voltage when said rectified voltage is less thansaid predetermined level and to convert said rectified voltage to saidhigh-frequency AC drive voltage when said rectified voltage is more thansaid predetermined level.
 20. The electronic ballast according to claim18, wherein said inverter is operable to convert said output voltage ofsaid boost converter to said high-frequency AC drive voltage when saidoutput voltage of said boost converter is greater than said rectifiedvoltage and to convert said rectified voltage to said high-frequency ACdrive voltage when said rectified voltage is greater than said outputvoltage of said boost converter.
 21. The electronic ballast according toclaim 4, wherein said ballast power supply further comprises asemiconductor switch coupled to conduct current from said AC powersupply when said semiconductor switch is conductive, and a transformerhaving a primary winding and a secondary winding, said primary windingcoupled in series electrical connection with said semiconductor switch;wherein said flyback control circuit is operable to receive saidrectified voltage and to repeatedly control said semiconductor switch tobe conductive and non-conductive at a high frequency to generate aboosted voltage across said secondary winding only when said rectifiedvoltage is below said predetermined level.
 22. The electronic ballastaccording to claim 21, wherein said high frequency and a duty cycle ofoperation of said semiconductor switch of said ballast power supply areconstant.
 23. The electronic ballast according to claim 22, wherein aninput impedance of the ballast is constant when said ballast powersupply is generating said boosted voltage when said rectified voltage isbelow said predetermined level.
 24. The electronic ballast according toclaim 21, wherein said secondary winding includes a tap for producing atap voltage less than said boosted voltage for generating saidsubstantially DC voltage.
 25. The electronic ballast according to claim7, wherein said second circuit comprises a boost converter having anoutput coupled to said inverter for supplying current to said inverter,and the first circuit comprises a diode.
 26. The electronic ballastaccording to claim 15, wherein said average magnitude of said DC outputvoltage is approximately one-half of said peak value of said rectifiedvoltage.
 27. A cat-ear circuit for an electronic ballast having a frontend for receiving an AC input voltage and a back end for driving a gasdischarge lamp comprising: an input for receipt of a rectified voltage;a semiconductor switch coupled in series electrical connection betweensaid input and a circuit common, said semiconductor switch having aconductive state and a non-conductive state; a transformer having aprimary winding and a secondary winding, said primary winding coupled inseries electrical connection with said semiconductor switch; a controlcircuit operable to receive said rectified voltage and to repeatedlyswitch said semiconductor switch at a high frequency between saidconductive state and said non-conductive state only when said rectifiedvoltage is below a predetermined level, such that a boosted voltage isproduced across said secondary winding of said transformer; a firstoutput for providing said boosted voltage to said ballast back end onlywhen said rectified voltage is below said predetermined level; and asecond output for providing a substantially low-magnitude DC voltage.